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ADP3166JRU-REEL7 Datasheet(PDF) 8 Page - Analog Devices |
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ADP3166JRU-REEL7 Datasheet(HTML) 8 Page - Analog Devices |
8 / 20 page REV. 0 –8– ADP3166 This amplifier can be configured several ways depending on the objectives of the system: • Output inductor ESR sensing without thermistor for lowest cost • Output inductor ESR sensing with thermistor for improved accuracy with tracking of inductor temperature • Sense resistors for highest accuracy measurements The positive input of the CSA is connected to the CSREF pin, which is connected to the output voltage. The inputs to the amplifier are summed together through resistors from the sensing element (such as the switch node side of the output inductors) to the inverting input, CSSUM. The feedback resistor between CSCOMP and CSSUM sets the gain of the amplifier, and a filter capacitor is placed in parallel with this resistor. The gain of the amplifier is programmable by adjusting the feedback resistor to set the load line required by the microprocessor. The current information is then given as the difference of CSREF – CSCOMP. This difference signal is used internally to offset the VID DAC for voltage positioning, and as a differential input for the current limit comparator. To provide the best accuracy for the sensing of current, the CSA has been designed to have a low offset input voltage. Also, the sensing gain is determined by external resistors so that it can be made extremely accurate. Active Impedance Control Mode For controlling the dynamic output voltage droop as a function of output current, a signal proportional to the total output cur- rent at the CSCOMP pin can be scaled to be equal to the droop impedance of the regulator times the output current. This droop voltage is then used to set the input control voltage to the sys- tem. The droop voltage is subtracted from the DAC reference input voltage directly to tell the error amplifier where the output voltage should be. This differs from previous implementations and allows enhanced feed-forward response. Voltage Control Mode A high gain-bandwidth voltage mode error amplifier is used for the voltage mode control loop. The control input voltage to the positive input is set via the VID 5-bit logic code according to the voltages listed in Table I. This voltage is also offset by the droop voltage for active positioning of the output voltage as a function of current, commonly known as active voltage position- ing. The output of the amplifier is the COMP pin, which sets the termination voltage for the internal PWM ramps. The negative input (FB) is tied to the output sense location with a resistor, RB, and is used for sensing and controlling the output voltage at this point. A current source from the FB pin flowing through RB is used for setting the no-load offset voltage from the VID voltage. The no-load voltage will be positive with respect to the VID DAC. The main loop compensation is incorporated in the feedback network between FB and COMP. Soft Start The power-on ramp-up time of the output voltage is set with a capacitor and resistor in parallel from the DELAY pin to ground. The RC time constant also determines the current limit latch-off time, as explained in the following section. In UVLO or when EN is a logic low, the DELAY pin is held at ground. After the UVLO threshold is reached and EN is a logic high, the DELAY capacitor is charged up with an internal 20 µA current source. The output voltage follows the ramping voltage on the DELAY pin, limiting the inrush current. The soft start time depends on the value of VID DAC and CDLY, with a secondary effect from RDLY. Refer to the Applications section for detailed information on setting CDLY. When the PWRGD threshold is reached, the soft start cycle is stopped and the DELAY pin is pulled up to 3 V. This ensures that the output voltage is at the VID voltage when the PWRGD signals to the system that the output voltage is good. If EN is taken low or if VCC drops below UVLO, the DELAY capacitor is reset to ground to be ready for another soft start cycle. Current Limit and Short-Circuit Protection The ADP3166 compares a programmable current limit set point to the voltage on the output of the current sense amplifier at the CSCOMP pin. The level of current limit is set with the resistor from the ILIMIT pin to ground. During normal operation, the voltage on ILIMIT is 3 V. The current through the external resistor is internally scaled to give a current limit threshold of 10.4 mV/ µA. If the difference in voltage between CSREF and CSCOMP drops below the current limit threshold, the internal current limit amplifier will control the internal COMP voltage to maintain the average output current at the limit. After the limit is reached, the 3 V pull-up on the DELAY pin is disconnected, and the external delay capacitor is discharged through the external resistor. A comparator monitors the DELAY voltage and shuts off the controller when the voltage drops below 1.8 V. The current limit latch-off delay time is therefore set by the RC time constant discharging from 3 V to 1.8 V. The Applications section discusses the selection of RDLY based on the CDLY that has been chosen. Because the controller continues to cycle the phases during the latch-off delay time, if the short is removed before the 1.8 V threshold is reached, the controller will return to normal operation. The recovery characteristic depends on the state of PWRGD. If the output voltage is within the PWRGD window, the controller resumes normal operation. However, if short circuit has caused the output voltage to drop below the PWRGD threshold, then a soft start cycle is initiated. The latch-off function can be reset by either removing and reapplying VCC to the ADP3166, or by pulling the EN pin low for a short time. To disable the short-circuit latch-off function, the external resistor to ground should be left open, and a large (greater than 1 M Ω) resistor should be connected from VCC to DELAY. This prevents the DELAY capacitor from discharging so the 1.8 V threshold is never reached. The resistor will have an impact on the soft start time because the current through it will add to the internal 20 µA current source. During startup when the output voltage is below 200 mV, a secondary current limit is active. This is necessary because the voltage swing of CSCOMP cannot go below ground. This sec- ondary current limit controls the internal COMP voltage to the PWM comparators to 2 V. This will limit the voltage drop across the low-side MOSFETs through the current balance circuitry. |
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