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VG025-G Datasheet(PDF) 2 Page - WJ Communication. Inc. |
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VG025-G Datasheet(HTML) 2 Page - WJ Communication. Inc. |
2 / 7 page Specifications and information are subject to change without notice WJ Communications, Inc • Phone 1-800-WJ1-4401 • FAX: 408-577-6621 • e-mail: sales@wj.com • Web site: www.wj.com Page 2 of 7 January 2006 VG025 High Linearity Variable Gain Amplifier Product Information The Communications Edge TM Application Circuit Configurations Circuit Board Material: .014” FR-4, 4 layers, .062” total thickness The WJ VG025 variable gain amplifier can operate over a very broad range of frequencies (50 - 2200MHz), but needs specific matching circuits for specific bands of interest. At the maximum gain state, reasonable matching is only available for about ±10% of the reference frequency. The amplifier operates with a typical current of 150 mA at +5 V while the attenuator current can be varied from 0 to 30 mA, while maintaining constant OIP3 and P1dB. The RF matching of the VG025 for the entire frequency range can be accomplished with the systematic adjustment of only a few parts. The RF matching is not influenced by different attenuator drive methods provided there is adequate decoupling of the attenuator bias. This reference application circuit uses voltage applied between 0 and 4.5V onto the Vctrl as shown on the schematic above. The R2 is a current limiting resistor to help linearize the drive of the attenuator and give better attenuator current control. To properly design the VG025 for an application, pick the frequency of interest. Choose blocking capacitor values which give RF impedance of less than 3 ohms. Choose the RF chokes for the largest inductance while still having resonant frequency about 30% greater than the Reference frequency (this allows for good isolation and inductor variation). Next choose L3 and C9 for interstage matching. C9 is only needed for lower frequencies and determines the low frequency roll off of the gain. L3 will have dominant control over the input and output return losses at maximum gain state (0 mA gain control pin current). C2 is needed to resonate the package parasitics to achieve the maximum attenuation values with attenuator current. With attenuator control pin current of 26 mA, C2 can be chosen to provide maximum attenuation. See the chart below for suggested component values and predicted performance at various reference frequencies. Component values can be interpolated for reference frequencies not listed. For lower frequencies the lumped element values can be used and the layout with unplaced component pads does not greatly affect the RF performance of the circuit. For frequencies greater than 500 MHz, component size and trace length have more influence on circuit performance. Smaller components and shorter trace lengths reduce the affects of the external component parasitics and interaction with the multichip module parasitics. Reference Frequency MHz 240 800 1850 1960 2140 C1, C5 pF 1000 56 56 56 56 C2 pF 0 Ω 27 3.6 3.6 3.6 C3, C4 μF .01 .01 .01 .01 .01 C6 pF DNP DNP DNP DNP DNP C9 pF 1.2 DNP DNP DNP DNP L1, L2 nH 220 22 12 12 12 L3 nH 47 8.2 DNP DNP DNP L4 nH DNP 82 33 33 33 R1 Ω DNP DNP DNP DNP DNP R2 Ω 120 120 120 120 120 Attenuation Range dB 20 21 12 14 13 Maximum Gain dB 15.4 15 8.6 8.4 8.4 Input Return Loss dB 11 6.3 11 12 11 Output Return Loss dB 11 7.6 7.7 6.5 5.6 Output P1dB dBm 21.8 21.3 22 22 22 Output IP3 dBm 42 39 40 40 40 Noise Figure dB 4.5 5.3 7.9 8.1 8.2 DNP = Do Not Place (Component is not used in the design) |
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