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LTC1041CS8 Datasheet(PDF) 5 Page - Linear Technology |
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LTC1041CS8 Datasheet(HTML) 5 Page - Linear Technology |
5 / 8 page LTC1041 5 1041fa APPLICATIO S I FOR ATIO RS • CIN. The ability to fully charge CIN from the signal source during the controller’s active time is critical in determining errors caused by the input charging current. For source resistances less than 10k Ω, CIN fully charges and no error is caused by the charging current. For RS > 10kΩ For source resistances greater than 10k Ω, CIN cannot fully charge, causing voltage errors. To minimize these errors, an input bypass capacitor, CS, should be used. Charge is shared between CIN and CS, causing a small voltage error. The magnitude of this error is AV = VIN • CIN (CIN + CS). This error can be made arbitrarily small by increasing CS. The averaging effect of the bypass capacitor, CS, causes another error term. Each time the input switches cycle between the plus and minus inputs, CIN is charged and discharged. The average input current due to this is IAVG = VIN • CIN • fS, where fS is the sampling frequency. Because the input current is directly proportional to the differential input voltage, the LTC1041 can be said to have an average input resistance of RIN = VIN/IAVG = I/(fS • CIN). Since two comparator inputs are connected in parallel, RIN is one half of this value (see typical curve of RIN versus Sampling Frequency). This finite input resistance causes an error due to the voltage divider between RS and RIN. The input voltage error caused by both of these effects is VERROR = VIN [2CIN/(2CIN + CS) + RS/(RS + RIN)]. Example: assume fS = 10Hz, RS = 1M, CS = 1µF, VIN = 1V, VERROR = 1V(66µV + 660µV) = 726µV. Notice that most of the error is caused by RIN. If the sampling frequency is reduced to 1Hz, the voltage error from the input impedance effects is reduced to 136 µV. Figure 2. Equivalent Input Circuit VIN RS CS LTC1041 • AI01 S1 S2 CIN ( ≈ 33pF) V– LTC1041 DIFFERENTIAL INPUT + – Input Voltage Range The input switches of the LTC1041 are capable of switching either to the V+ supply or ground. Consequently, the input voltage range includes both supply rails. This is a further benefit of the sampling input structure. Error Specifications The only measurable errors on the LTC1041 are the deviations from “ideal” of the upper and lower switching levels (Figure 1b). From a control standpoint, the error in the SET POINT and deadband is critical. These errors may be defined in terms of VU and VL. SET POINT error V SET POINT deadband error V U U ≡ + ≡ () V V DELTA L L 2 2 – –– • The specified error limits (see electrical characteristics) include error due to offset, power supply variation, gain, time and temperature. Pulsed Power (VP-P) Output It is often desirable to use the LTC1041 with resistive networks such as bridges and voltage dividers. The power consumed by these resistive networks can far exceed that of the LTC1041 itself. At low sample rates the LTC1041 spends most of its time off. A switched power output, VP-P, is provided to drive the input network, reducing its average power as well. VP-P is switched to V+ during the controller’s active time ( ≈ 80µs) and to a high impedance (open circuit) when internal power is switched off. Figure 3 shows the VP-P output circuit. The VP-P output voltage is not precisely controlled when driving a load (see typical curve of VP-P Output Voltage vs Load Current). In spite of this, high precision can be achieved in two ways: (1) driving ratiometric networks and (2) driving fast set- tling references. In ratiometric networks all the inputs are proportional to VP-P (Figure 4). Consequently, the absolute value of VP-P does not affect accuracy. |
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