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MIC2169 Datasheet(PDF) 11 Page - Micrel Semiconductor |
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MIC2169 Datasheet(HTML) 11 Page - Micrel Semiconductor |
11 / 15 page March 2009 11 M9999-032409 MIC2169 Micrel 100 1.103 1.104 1.105 1.106 150 100 50 0 0 180 1000000 100 f Figure 5. Phase Curve for G(s) It can be seen from the transfer function G(s) and the gain curve that the output inductor and capacitor create a two pole system with a break frequency at: f 1 2L C LC OUT = ×× π Therefore, f LC = 3.6kHz By looking at the phase curve, it can be seen that the output capacitor ESR (0.025 Ω) cancels one of the two poles (LC OUT) system by introducing a zero at: f 1 2 ESR C ZERO OUT = ×× × π Therefore, F ZERO = 6.36kHz. From the point of view of compensating the voltage loop, it is recommended to use higher ESR output capacitors since they provide a 90° phase gain in the power path. For com- parison purposes, Figure 6 shows the same phase curve with an ESR value of 0.002 Ω. 100 1.103 1.104 1.105 1.106 150 100 50 0 0 180 1000000 100 f Figure 6. The Phase Curve with ESR = 0.002 Ω It can be seen from Figure 5 that at 50kHz, the phase is approximately –90° versus Figure 6 where the number is –150°. This means that the transconductance error ampli- fier has to provide a phase boost of about 45° to achieve a closed-loop phase margin of 45° at a crossover frequency of 50kHz for Figure 4, versus 105° for Figure 6. The simple RC and C2 compensation scheme allows a maximum error amplifier phase boost of about 90°. Therefore, it is easier to stabilize the MIC2169 voltage control loop by using high ESR value output capacitors. g m Error Amplifier It is undesirable to have high error amplifier gain at high frequencies because high frequency noise spikes would be picked up and transmitted at large amplitude to the output, thus, gain should be permitted to fall off at high frequencies.At low frequency, it is desireable to have high open-loop gain to attenuate the power line ripple. Thus, the error amplifier gain should be allowed to increase rapidly at low frequencies. The transfer function with R1, C1, and C2 for the internal g m error amplifier can be approximated by the following equation: Error Amplifier(z) g 1R1 S C1 sC1 C2 1 R1 C1 C2 S C1 C2 m =× +× × ×+ () +× ×× + ⎛ ⎝⎜ ⎞ ⎠⎟ ⎡ ⎣ ⎢ ⎢ ⎢ ⎢ ⎤ ⎦ ⎥ ⎥ ⎥ ⎥ The above equation can be simplified by assuming C2<<C1, Error Amplifier(z) g 1R1 S C1 s C1 1 R1 C2 S m =× +× × × () +× × () ⎡ ⎣ ⎢ ⎤ ⎦ ⎥ From the above transfer function, one can see that R1 and C1 introduce a zero and R1 and C2 a pole at the following frequencies: Fzero= 1/ 2 π × R1 × C1 Fpole = 1/ 2 π × C2 × R1 Fpole@origin = 1/ 2 π × C1 Figures 7 and 8 show the gain and phase curves for the above transfer function with R1 = 9.3k, C1 = 1000pF, C2 = 100pF, and g m = .005Ω –1. It can be seen that at 50kHz, the error amplifier exhibits approximately 45° of phase margin. 1.103 1.104 1.105 1.106 1.107 20 40 60 60 .001 10000000 1000 f Figure 7. Error Amplifier Gain Curve |
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Similar Description - MIC2169_09 |
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