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LT1513C Datasheet(PDF) 11 Page - Linear Technology |
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LT1513C Datasheet(HTML) 11 Page - Linear Technology |
11 / 16 page 11 LT1513/LT1513-2 APPLICATIONS INFORMATION Figure 7. Constant-Current Small-Signal Model problem, and indeed small signal loop stability can be excellent even in the presence of subharmonic switching. The primary issue with subharmonics is the presence of EMI at frequencies below 500kHz. Constant-Current Mode Loop Stability The LT1513 is normally very stable when operating in con- stant-current mode (see Figure 7), but there are certain con- ditions which may create instabilities. The combination of highervaluecurrentsenseresistors(lowprogrammedcharg- ing current), higher input voltages, and the addition of a loop compensation resistor (R5) on the VC pin may create an un- stable current mode loop. (A resistor is sometimes added in series with C5 to improve loop phase margin when the loop is operating in voltage mode.) Instability results because loop gain is too high in the 50kHz to 150kHz region where excess phase occurs in the current sensing amplifier and the modulator. The IFBA amplifier (gain of –12.5) has a pole at approximately 150kHz. The modulator section con- sisting of the current comparator, the power switch and the magnetics, has a pole at approximately 50kHz when the coupledinductorvalueis10 µH.Higherinductancewillreduce thepolefrequencyproportionally.Thedesignprocedurepre- sented here is to roll off the loop to unity-gain at a frequency of 25kHz or lower to avoid these excess phase regions. (from the Electrical Characteristics). Amplifier output resis- tance is modeled with a 330k resistor. The power stage (modulator section) of the LT1513 is modeled as a transcon- ductance whose value is 4(VIN)/(VIN + VBAT). This is a very simplified model of the actual power stage, but it is sufficient when the unity-gain frequency of the loop is low compared to the switching frequency. The output filter capacitor model includes its ESR (RCAP). A series resistance (RBAT) is also assigned to the battery model. Analysis of this loop normally shows an extremely stable system for all conditions, even with 0 Ω for R5. The one condition which can cause reduced phase margin is with a very large battery resistance (> 5 Ω), or with the battery replaced with a resistive load. The addition of R5 gives good phase margin even under these unusual conditions. R5 should not be increased above 330 Ω without checking for two possible problems. The first is instability in the constant current region (see Constant-Current Mode Loop Stability), and the second is subharmonic switching where switch duty cycle varies from cycle to cycle. This duty cycle instability is caused by excess switching frequency ripple voltage on the VC pin. Normally this ripple is very low because of the filtering effect of C5, but large values of R5 can allow high ripple on the VC pin.Normalloopanalysisdoesnotshowthis RP** 1M gm 1500 µmho IP MODULATOR SECTION IP = 4(V1)(VIN) VIN + VBAT V1 FB VC 1513 F07 1.245V EA IFBA VOLTAGE GAIN = 12 RG 330k R5 330 Ω C5 0.1 µF CA 10pF RA 100k R4 24 Ω R3 0.1 Ω CP 3pF C4 0.22 µF IFB THIS IS A SIMPLIFIED AC MODEL FOR THE LT1513 IN CONSTANT-CURRENT MODE. RESISTOR AND CAPACITOR NUMBERS CORRESPOND TO THOSE USED IN FIGURE 1. RP AND CP MODEL THE PHASE DELAY IN THE PowerPath. C3 IS 3pF FOR A 10 µH INDUCTOR. IT SHOULD BE SCALED PROPORTIONALLY FOR OTHER INDUCTOR VALUES (6pF FOR 20 µH). THE PowerPath IS A TRANSCONDUCTANCE WHOSE GAIN IS A FUNCTION OF INPUT AND BATTERY VOLTAGE AS SHOWN. THE CURRENT AMPLIFIER HAS A FIXED VOLTAGE GAIN OF 12. ITS PHASE DELAY IS MODELED WITH RA AND CA. THE ERROR AMPLIFIER HAS A TRANSCONDUCTANCE OF 1500 µmho AND AN INTERNAL OUTPUT SHUNT RESISTANCE OF 330k. AS SHOWN, THIS LOOP HAS A UNITY-GAIN FREQUENCY OF ABOUT 27kHz. R5 IS NOT USED IN ALL APPLICATIONS, BUT IT GIVES BETTER PHASE MARGIN IN CONSTANT VOLTAGE MODE. |
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