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PCM1750UG4 Datasheet(PDF) 8 Page - Texas Instruments |
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PCM1750UG4 Datasheet(HTML) 8 Page - Texas Instruments |
8 / 21 page ® PCM1750 8 occurs during the SAMPLE period (see the timing diagram shown in Figure 2). These errors are stored on the AC coupling capacitors (CAZ1 to CAZ4, shown in Figure 1) between the gain stages. During the SAMPLE period the inputs to gain stages A1 and A2 and the latch are grounded by switches H1, H2, and AZ1 to AZ4. Capacitors CAZ1 and CAZ2 track the amplified offset voltage of gain stage A1 and capacitors CAZ3 and CAZ4 do the same for A2. At the beginning of a conversion cycle, the autozeroing switches open and the instantaneous amplified value of both the DC offset voltage and the low-frequency flicker noise is stored on the coupling capacitors to produce zero comparator offset during a conversion cycle. SUCCESSIVE APPROXIMATION CONVERSION PROCESS The timing diagram in Figure 2 illustrates the successive approximation routine of the PCM1750. Control signals CONVERT and CLK are derived from a master system clock which comes from a 256fS (256 X the base sampling frequency of 48kHz) clock used by the optional digital filter. There are 64 clocks shown in the timing diagram because the PCM1750 is shown operating at 4 times the standard 48kHz sample rate (192kHz). Several events occur on the rising edge of the CONVERT command. Switches AZ1 to AZ4, H1 and H2 open and switch S1 reconnects the MSB capacitor, C1, from VIN to analog common (see Figure 1). This terminates the com- parator auto-zero cycle and simultaneously switches (co- phase sampling) both converters from tracking their respec- tive input signals into the HOLD mode, thus capturing the instantaneous value of VIN (with a small delay specified as the aperture time). At the start of a conversion cycle when S1 is switched to analog common, the sampled input signal VIN will appear at the comparator input as –VIN/2 due to the 2-to-1 capacitive divider action of Cl = C2 + C3 + ... C18. In a somewhat similar manner, VREF is transferred to the comparator input as –VREF/2 to create a bipolar offset. The 19-bit shift register, shown in Figure 4, controls testing of the bits of the dual ADCs beginning with bit-1 (MSB) and proceeding one bit at a time to bit-18 (LSB), leaving ON those bits that don’t cause the cumulative value of the CDAC to exceed the original input value and leaving OFF those bits that do. Since the bits of both channels are tested together, only one shift register is required to control both ranks of 18 data latches. For example, the testing of bit-2 proceeds in the following manner. The positive pulse from the second shift register element SR2, (see Figure 2 and 4) is applied to the bit-2 data latch and NOR gate. The NOR gate in turn drives S2 and switches bit-2 at the beginning of the bit-2 test interval. Note that the bit interval must be long enough to allow both the comparator input to settle and the comparator to respond. On 1 2 18 19 3 *Optional Digital Filter 54 55 56 57 58 59 60 61 62 63 64 1 23 4 5 6 78 9 10 11 12 T1 T4 T6 T3 T5 T7 T9 REF T Convert Ext Clk In SOUT Bit 18 LSB Bit 1 MSB Bit 2 Bit 17 T8 T2 PARAMETER DESCRIPTION MIN NOMINAL MAX UNITS T1 (1 x TREF) Convert Command High 24 33 55 % of T4 T2 (6 x TREF) S/H Acquisition Time 420 486 ns T3 (4 x TREF) Convert to Clock time 281 326 1302 ns T4 (3 x TREF) Master Clock Input 211 244 977 ns T5 (1 x TREF) Clock High 24 33 55 % of T4 T6 (2 x TREF) Clock Low 45 67 76 % of T4 T7 Data Hold Time 10 ns T8 Data Setup Time 100 ns T9 Data Valid Time 120 154 1212 ns TCONV (64 x TREF) Conversion Throughput Time 4.5 5.2 20.8 µs TREF (Sample Rate /64) Ext Digital Filter Clock 70 81 326 ns Note: The nominal timing shown in this diagram is all done automatically by the DF1750 digital filter. Only the optional digital filter clock is required when the DF1750 is used. FIGURE 3. PCM1750 Setup and Hold Timing Diagram. |
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Similar Description - PCM1750UG4 |
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