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ADP3121 Datasheet(PDF) 6 Page - ON Semiconductor |
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ADP3121 Datasheet(HTML) 6 Page - ON Semiconductor |
6 / 10 page ADP3121 http://onsemi.com 6 OD going high. If this second latch is set, then OVP is enabled. To clear the OVP or the input detected latch, VCC must fall below UVLO. Supply Capacitor Selection For the supply input (VCC) of the ADP3121, a local bypass capacitor is recommended to reduce the noise and to supply some of the peak currents that are drawn. Use a 4.7 mF, low ESR capacitor. Multilayer ceramic chip (MLCC) capacitors provide the best combination of low ESR and small size. Keep the ceramic capacitor as close as possible to the ADP3121. Bootstrap Circuit The bootstrap circuit uses a charge storage capacitor (CBST) and a diode, as shown in Figure 1. These components can be selected after the high−side MOSFET is chosen. The bootstrap capacitor must have a voltage rating that can handle twice the maximum supply voltage. A minimum 50 V rating is recommended. The capacitor values are determined by CBST1 ) CBST2 + 10 QGATE VGATE (eq. 1) CBST1 CBST1 ) CBST2 + VGATE VCC * VD (eq. 2) where: QGATE is the total gate charge of the high−side MOSFET at VGATE. VGATE is the desired gate drive voltage (usually in the range of 5 V to 10 V, 7 V being typical). VD is the voltage drop across D1. Rearranging Equation 1 and Equation 2 to solve for CBST1 yields CBST1 + 10 QGATE VCC * VD CBST2 can then be found by rearranging Equation 1 CBST2 + 10 QGATE VGATE * CBST1 For example, an NTD60N02 has a total gate charge of about 12 nC at VGATE = 7 V. Using VCC = 12 V and VD = 0.1 V, then CBST1 = 12 nF and CBST2 = 6.8 nF. Good quality ceramic capacitors should be used. RBST is used to limit slew rate and minimize ringing at the switch node. It also provides peak current limiting through D1. An RBST value of 1.5 W to 2.2 W is a good choice. The resistor needs to handle at least 250 mW due to the peak currents that flow through it. A small signal diode can be used for the bootstrap diode due to the ample gate drive voltage supplied by VCC. The bootstrap diode must have a minimum 15 V rating to withstand the maximum supply voltage. The average forward current can be estimated by IF(AVG) + QGATE fMAX (eq. 3) where fMAX is the maximum switching frequency of the controller. The peak surge current rating should be calculated by IF(PEAK) + VCC * VD RBST (eq. 4) MOSFET Selection When interfacing the ADP3121 to external MOSFETs, the designer should consider ways to make a robust design that minimizes stresses on both the driver and the MOSFETs. These stresses include exceeding the short time duration voltage ratings on the driver pins as well as the external MOSFET. It is also highly recommended to use the Boot−Snap circuit to improve the interaction of the driver with the characteristics of the MOSFETs. If a simple bootstrap arrangement is used, make sure to include a proper snubber network on the SW node. High−Side (Control) MOSFETs A high−side, high speed MOSFET is usually selected to minimize switching losses (see the ADP3186 or ADP3188 data sheet for Flex−Mode controller details). This typically implies a low gate resistance and low input capacitance/charge device. Yet, a significant source lead inductance can also exist that depends mainly on the MOSFET package; it is best to contact the MOSFET vendor for this information. The ADP3121 DRVH output impedance and the input resistance of the MOSFETs determine the rate of charge delivery to the internal capacitance of the gate. This determines the speed at which the MOSFETs turn on and off. However, because of potentially large currents flowing in the MOSFETs at the on and off times (this current is usually larger at turn−off due to ramping up of the output current in the output inductor), the source lead inductance generates a significant voltage when the high−side MOSFETs switch off. This creates a significant drain−source voltage spike across the internal die of the MOSFETs and can lead to a catastrophic avalanche. The mechanisms involved in this avalanche condition are referenced in literature from the MOSFET suppliers. The MOSFET vendor should provide a rating for the maximum voltage slew rate at drain current around which this can be designed. Once this specification is obtained, determine the maximum current expected in the MOSFET by IMAX + IDC(per phase) ) (VCC * VOUT) DMAX fMAX LOUT (eq. 5) where: DMAX is determined for the VR controller being used with the driver. This current is divided roughly equally between MOSFETs if more than one is used (assume a worst−case mismatch of 30% for design margin). LOUT is the output inductor value. |
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