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LM7372MR Datasheet(PDF) 11 Page - National Semiconductor (TI) |
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LM7372MR Datasheet(HTML) 11 Page - National Semiconductor (TI) |
11 / 15 page Application Notes (Continued) For each amplifier then, with an effective load each of R L and a sine wave source, integration over the half cycle with a supply voltage V S and a load voltage VL yields the average power dissipation P D =VSVL/πRL -VL 2/2R L..........(1) Where V S is the supply voltage and VL is the peak signal swing across the load R L. For the package, the power dissipation will be doubled since there are two amplifiers in the package, each contributing half the swing across the load. The circuit in Figure 1 is using the LM7372 as the upstream driver in an ADSL application with Discrete MultiTone modu- lation. With DMT the upstream signal is spread into 32 adjacent channels each 4kHz wide. For transmission over POTS, the regular telephone service, this upstream signal from the CPE (Customer Premise Equipment) occupies a frequency band from around 20kHz up to a maximum fre- quency of 135kHz. At first sight, these relatively low trans- mission frequencies certainly do not seem to require the use of very high speed amplifiers with GBW products in the range of hundreds of megahertz. However, the close spac- ing of multiple channels places stringent requirements on the linearity of the amplifier, since non-linearities in the presence of multiple tones will cause harmonic products to be gener- ated that can easily interfere with the higher frequency down stream signals also present on the line. The need to deliver 3rd Harmonic distortion terms lower than −75dBc is the reason for the LM7372 quiescent current levels. Each am- plifier is running over 3mA in the output stage alone in order to minimize crossover distortion. xDSL signal levels are adjusted to provide a given power level on the line, and in the case of ADSL this is an average power of 13dBm. For a line with a characteristic impedance of 100 Ω this is only 20mW. Because the transformer shown in Figure 1 is part of a transceiver circuit, two back-termination resistors are connected in series with each amplifier output. Therefore the equivalent R L for each ampli- fier is also 100 Ω, and each amplifier is required to deliver 20mW to this load. Since V L 2/2RL = 20mW then V L = 2V(peak). Using Equation (1) with this value for signal swing and a 24V supply, the internal power dissipation per amplifier is 132.8mW. Adding the quiescent power dissipation to the amplifier dissipation gives the total package internal power dissipation as P D(Total) = 312mW + (2 x 132.8mW) = 578mW This result is actually quite pessimistic because it assumes that the dissipation as a result of load current is simply added to the dissipation as a result of quiescent current. This is not correct since the AB bias current in the output stage is diverted to load current as the signal swing amplitude in- creases from zero. In fact with load currents in excess of 3.3mA, all the bias current is flowing in the load, conse- quently reducing the quiescent component of power dissipa- tion. Also, it assumes a sine wave signal waveform when the actual waveform is composed of many tones of different phases and amplitudes which may demonstrate lower aver- age power dissipation levels. The average current for a load power of 20mW is 14.1mA. Neglecting the AB bias current this appears as a full-wave rectified current waveform in the supply current with a peak value of 19.9mA. The peak to average ratio for a waveform of this shape is 1.57, so the total average load current is 12.7mA. Adding this to the quiescent current, and subtract- ing the power dissipated in the load gives the same package power dissipation level calculated above. Nevertheless, when the supply current peak swing is measured, it is found to be significantly lower because the AB bias current is contributing to the load current. The supply current has a peak swing of only 14mA (compared to 19.9mA) superim- posed on the quiescent current, with a total average value of only 21mA. Therefore the total package power dissipation in this application is P D(Total) =(VS x Iavg) - Power in Load = (24 x 21)mW - 40mW = 464mW This level of power dissipation would not take the junction temperature in the SO-8 package over the absolute maxi- mum rating at elevated ambient temperatures (barely), but there is no margin to allow for component tolerances or signal variances. To develop 20mW in a 100 Ω requires each amplifier to deliver a peak voltage of only 2V, or 4V( P-P). This level of signal swing does not require a high supply voltage but the application uses a 24V supply. This is because the modula- tion technique uses a large number of tones to transmit the data. While the average power level is held to 20mW, at any time the phase and amplitude of individual tones will be such as to generate a combined signal with a higher peak value than 2V. For DMT this crest factor is taken to be around 5.33 so each amplifier has to be able to handle a peak voltage swing of V Lpeak = 1.4 x 5.33 = 7.5V or 15V(P-P) If other factors, such as transformer loss or even higher peak to average ratios are allowed for, this means the amplifiers must each swing between 16 to 18V( P-P). The required signal swing can be reduced by using a step-up transformer to drive the line. For example a 1:2 ratio will reduce the peak swing requirement by half, and this would allow the supply to be reduced by a corresponding amount. This is not recommended for the LM7372 in this particular application for two reasons. Although the quiescent power contribution to the overall dissipation is reduced by about 150mW, the internal power dissipation to drive the load remains the same, since the load for each amplifier is now 25 Ω instead of 100Ω. Furthermore, this is a transceiver application where downstream signals are simultaneously appearing at the transformer secondary. The down stream signals appear differentially across the back termination re- sistors and are now stepped down by the transformer turns ratio with a consequent loss in receiver sensitivity compared to using a 1:1 transformer. Any trade-off to reduce the supply voltage by an increase in turns ratio should bear these factors in mind, as well as the increased signal current levels required with lower impedance loads. At an elevated ambient temperature of 85˚C and with an average power dissipation of 464mW, a package thermal resistance between 60˚C/W and 80˚C/W will be needed to keep the maximum junction temperature in the range 110˚C to 120˚C. The PSOP or LLP package would be the package of choice here with ample board copper area to aid in heat dissipation (see table 2). For most standard surface mount packages, SO-8, SO-14, SO-16 etc, the only means of heat removal from the die is through the bond wires to external copper connecting to the leads. Usually it will be difficult to reduce the thermal resis- www.national.com 11 |
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